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САНКТ-ПЕТЕРБУРГСКИЙ ГОСУДАРСТВЕННЫЙ ТЕХНИЧЕ=
СКИЙ
УНИВЕРСИТЕТ
А.Г. ЛЕОНТЬЕВ
КУРС ЛЕКЦИЙ ПО ЭЛЕКТРОМЕХАНИКЕ=
span>
1.
Датчики обратной связи и первичная обработка сигналов датчиков. =
1.1 Тахогенераторы постоянного тока.<=
/p>
Тахогенера=
торы
являются датчиками частоты вращения, преобразующими частоту вращения w в напряжение постоянного тока Uтг.
Статика.
Электрическая схема ТГ
показана на рис.
1-1a, а эквивалентная схема якорной цепи на рис. 1-1б<=
/a>.
Статика ТГ описывается тр=
емя
уравнениями (1-1),
из которых можно получить статическую характеристику ТГ "вход-выход&qu=
ot; (1-2),=
где Kтг
– коэффициент передачи тахогенератора, который зависит от сопротивления
нагрузки Rн и
потока возбуждения Фв=
(1-3)=
a>.
Статические
характеристики ТГ показаны на рис. 1-2=
a>, где
Rн2 < Rн1.
Уменьшение Kтг (наклона характеристики) при увеличении нагрузки
понятно из формулы (1-2), а искривление характеристики при больших сигналах
объясняется уменьшением потока возбуждения Фв из-за =
реакции
якоря. Нормальный режим работы ТГ обеспечивается при небольших нагрузках, к=
огда
Фв=3Dconst.
Динамика.
Инерционно=
сть ТГ
объясняется электрической инерционностью его якорной цепи из-за индуктивнос=
ти
обмотки якоря .
Эквивалент=
ная
схема якорной цепи с учетом индуктивности якоря показана на рис. 1-3=
a>.
Динамика процесса в якорной цепи описывается тремя уравнениями (1-4) в
операторной форме. Из этих уравнений может быть получена передаточная функц=
ия
ТГ как динамического объекта – (1-5).=
Переходный процесс в ТГ при ступенчатом изменении
скорости показан на рис. 1-4. Быстродействие ТГ можно оценить по времени
переходного процесса Тп,
которое зависит от постоянной времени Tтг,
которое в свою очередь зависит от нагрузки – Rн. Таким=
образом
для улучшения и статических и динамических характеристик ТГ необходимо
увеличивать сопротивление нагрузки Rн, т.е. ТГ должен работать в режиме, близком к холост=
ому
ходу.
1.2
Синусно_косинусные
вращающиеся трансформаторы (СКВТ).
Принцип
действия СКВТ.
СКВТ – гиб=
рид
асинхронной машины и трансформатора. Имеет по две взаи=
моперпендикулярных
обмотки на статоре – главную Г1-Г2 и вспомогательную В1-В2, и две на роторе=
–
синусную и косинусную – рис.1-5.
СКВТ выпол=
няет
функцию датчика угла поворота, преобразуя угол поворота a
в один из параметров (в зависимости от режима работы) сигнала переменного т=
ока,
снимаемого с роторной обмотки – Ups.
Обычно одн=
а или
обе статорные обмотки СКВТ запитываются напряже=
нием
переменного тока повышенной частоты (500 -10000 Гц). Эти напряжения
трансформируются в роторные обмотки с учетом коэффициента трансформации,
который в СКВТ зависит от угла поворота ротора a
по синусному и косинусному закону.
В общем виде напряжение, трансформированное, например, в
синусную обмотку, выражается формулой (1-6),=
а в
косинусную – формулой (1-7).
Основные
режимы работы СКВТ.
1. Амплитудный индикаторный режим.
В этом режиме запитывается
только главная статорная обмотка. Тогда при подстановке в основную формулу
(1-6) получим выражение для напряжения на роторной обмотке Ups в виде формулы (1-8),=
где Ups м – амплитуда переменного напряжения=
на
роторной синусной обмотке.
Таким образом в этом режим=
е СКВТ
преобразует угол поворота a в амп=
литуду
выходного напряжения, которая меняется, как показано на рис. 1-6=
a>. При
вращении ротора происходит амплитудная модуляция выходного сигнала, как
показано на рис.
1-7.
2. Фазовый индикаторный ре=
жим.
В этом
режиме статорные обмотки запитываются напряжениеми, сдвинутыми во времени на 90°. При подст=
ановке
этих выражений в основную формулу (1-6) получим выражение для выходного
напряжения в виде (1-9). Как видно из этого выражения, здесь фаза выходного
напряжения зависит от угла поворота a,
как это показано на рис. 1-8. Из этого рисунка видно, что угол поворота
преобразуется во временной интервал t
, который может менятьс=
я в
пределах половины периода питания 0,5T=
, как
это показано на рис. 1-9. Как видно из рисунка, это линейная периодическая
функция с периодом от -p до +p, то есть преобразование происходит
внутри одного оборота ротора (полоборота в одну
сторону и полоборота – в другую). Временной инт=
ервал
легко преобразовать в цифровой код, поэтому СКВТ в таком режиме может
использоваться в цифровых следящих системах, имеющих структур=
у,
показанную на рис.
1-10.
Здесь введены следующие обозначения: =
·&nb=
sp; =
&nb=
sp; =
ПК –
программируемый контроллер;
·&nb=
sp; =
&nb=
sp; =
ЦАП –
цифроаналоговый преобразователь;
·&nb=
sp; =
&nb=
sp; =
РП –
регулируемый привод;
·&nb=
sp; =
&nb=
sp; =
ИД –
исполнительный двигатель;
·&nb=
sp; =
&nb=
sp; =
ФОН –
формирователь опорных напряжений.
ПК – выполняет роль программного задат=
чика
и регулятора. Он задает код заданного угла Na з и вычисляет сигнал рассогласования Na=3D Na з-Na, который по заданному
закону управления (например, пропорциональному) через ЦАП преобразуется в
напряжение управления Uу
и через силовые элементы РП выдает напряжение Uд на исполнительный двигатель. Дви=
гатель
через редуктор поворачивает ротор СКВТ, сигнал с которого преобразуется в к=
од
заданного угла Na з – обратная
связь по положению (углу поворота). Благодаря наличию обратной связи следящ=
ая
система работает так, что угол поворота ротора a
равен заданному углу aз (с погрешно=
стью,
зависящей от параметров системы), т.е. это следящая система.
3. Фазовый разностный режим.
В этом режиме с помощью управляемого формирователя
опорных напряжений статорные обмотки СКВТ запитываются=
синусоидальными сигналами, которые, как видно из формул (1-10)=
, могут
менять фазу в зависимости от заданного угла aз. Подставив эти выражения в
основную формулу (1-6), получим выражение (1-11),
аналогичное (1-9). Здесь фаза выходного напряжения Uрs зависит от разности заданног=
о и
фактического углов aз-a,
т.е. СКВТ сам вычисляет сигнал рассогласования и является элементом а=
втономной
следящей системы, структура которой показана на рис. 1-11<=
/a>.
Здесь ПК выполняет функцию задатчика, управляя =
ФОН-ом
по формуле (1-11), выходной сигнал СКВТ Uрs выпря=
мляется
фазовым детектором ФД, превращаясь в сигнал рассогласования e, который через регулируемый привод РП у=
правляет
исполнительным двигателем ИД. При достаточно большом коэффициенте усиления РП систе=
ма
стремится поддерживать e»0<=
/u>,
т.е. a»aз.
4. Амплитудный разностный режим.
В этом режиме статорные обмотки СКВТ также запитываются от управляемого функционального ФОН-а, который, как видно из формул (1-12)=
, может
менять амплитуду подаваемых на СКВТ напряжений в зависимости =
от
заданного угла aз. Подста=
вив эти
выражения в (1-6), получим выражение для выходного сигнала СКВТ (1-13)=
. Как
видно из этой формулы, здесь амплитуда выходного сигнала Uрs м зависит от разности углов aз-a, по
синусоидальному закону, как показано на рис. 1-12<=
/a>.
Структура автономной следящей системы с СКВТ, работаю=
щем
в этом режиме показана на рис. 1-13. Она отличается от схемы рис. 1-11 другим типом=
ФОН-а и наличием фазочувствитель=
ного
выпрямителя ФЧВ,
который преобразует выходной сигнал СКВТ Uрs в сигнал рассогласования
постоянного тока e.
Система должна обладать такими динамическими свойствами, чтобы сигнал
рассогласования не выходил за рабочий =
участок,
показанный на рис. 1-12.
1.3 Инкрементные фотоимпуль=
сные
датчики (ФИД).
Схема прим=
енения
фотоимпульсного датчика для измерения угла пово=
рота a показана на рис. 1-14<=
/a>.
Основным
элементом ФИД является прозрачный диск=
с
нанесенными на него рисками, количество которых достигает нескольких тысяч.=
При
повороте диска, луч света, излучаемый источником ИС,
модулируется рисками и воспринимается фотоприемниками ФП.
Электрические сигналы от ФП преобразуются электронным преобразователем ЭП в=
систему
электрических сигналов, которые подаются на программируемый контроллер ПК. =
ФИД генерирует следующие сигналы и их инверсии:
- OSN
– основной;
- SM –
смещенный;
- CLRM
– нуль-метод.
Диаграмма этих сигналов при вращен=
ии
вправо и влево показана на рис. 1-15. Программно-аппаратное обеспечение ПК организов=
ано
так, что при движении вправо при каждом переходе входного сигнала происходи=
т прибавле=
ние
"1" в программном или аппаратном счетчике, а при движен=
ии
влево – вычитание
"1". Кроме того, ПК проверяет отсутствие обрыва линии,
сравнивая сигналы с их инверсиями. Таким образом, в счетчике ПК
формируется код угла поворота Na или его приращения. =
2.
Разомкнутые системы управления двигателями.
2.1
Управление двигателями постоянного тока (ДПТ).
Якорное
управление с усилителем мощности (УМ).
Функционал=
ьная
схема системы управления ДПТ показана на рис. 1-16=
. В
зависимости от варианта системы получаются различные механические
характеристики двигателя, показанные на рис. 1-17=
.
Естественн=
ая
механическая характеристика ДПТ описывается формулой (1-14). При
подключении УМ с выходным сопротивлением Rвых происходит ухудшение характери=
стики (1-15).
Для улучше=
ния
характеристики вводят обратную связь по напряжению с коэффициентом Kос U, которая уменьшает влияние Rвых (1-16). Для
большей коррекции механической характеристики (приближения ее к горизон=
тальной)
возможно введение положительной обратно=
й связи
по току с коэффициентом Kос I (1-17).
Тиристорное=
span> управление ДПТ.
Схема простейшего тиристорного уп=
равления
ДПТ показана на рис. 1-18. Схема состоит из силовой части – управляемого
выпрямителя – УВ и системы импульсного фазового управления – СИФУ. СИФУ,
как показано на рис. 1-19, с помощью генератора пилообразного напряжения и
компаратора формирует импульсы управления тиристорами Uу1 и Uу2=
,
причем положение этих импульсов внутри полупериода питания зависит от велич=
ины
входного напряжения Uвх.
При попеременном включении тиристоров Т1 =
и Т2
на якорь двигателя подается пульсирующее напряжение Uдв, сред=
нее
значение которого пропорционально площади, заштрихованной на рис. 1-19, и
вычисляется по формуле (1-18). Зависимость выходного напряжения УВ, подаваемого =
на
двигатель, от угла включения тиристоров =
a=
span>
показана на рис.
1-20а, а характеристика "вход-выход" – на рис. 1-20=
б,
где U – действующее значение напряжений U1 и U2=
span>
Импульсное управление ДПТ.
При импуль=
сном
управлении якорь ДПТ периодически подключается к источнику питания через
транзисторный ключ, с помощью широтно-импульсного преобразователя – ШИП, как
показано на рис.
1-21.
Временная
диаграмма работы системы импульсного управления с широтно-импульсной модуля=
цией
– ШИМ приведена на рис. 1-22. ШИП преобразует входное напряжение в длительно=
сть
импульса tи при не=
изменном
периоде квантования Т=
span>
. При этом на двигатель
подается импульсное напряжение, среднее значение которого Uдв завис=
ит от
соотношения длительности импульса и периода – скважности g=3Dtи=
span>/T (1-19). Механическая
характеристика ДПТ в такой системе выражается формулой (1-20) и
имеет вид, показанный на рис. 1-23.
Система
импульсного управления обладает достаточно высоким быстродействием, т.к. ШИП
обеспечивает довольно большую частоту квантования – несколько килогерц, т.е=
. Т£1 мс.
2.2
Управление трехфазными асинхронными двигателями (АД).
Амплитудное
управление.
Амплитудное управление воз=
можно
такими АД, которые имеют "мягкую" механическую характеристику и п=
ри
наличии обратной связи по скорости, как показано на рис. 1-24=
.
В данной схеме вентильный преобразователь ВП =
меняет
величину напряжения U, подаваемого на двигатель, в зависимости от управляющего
сигнала Uу,
поступающего от операционного усилителя ОУ. ОУ меняет =
Uу так,=
чтобы
напряжения на его входах были равны, т.е. wз=3Dw. =
Таким образом, как показано на рис. 1-25=
, в
некотором диапазоне нагрузок М рабочая=
точка
переходит с одной характеристики на другую из-за изменения напряжения U, =
что
приводит к поддержанию постоянной частоты вращения w равной заданной, т.е. характеристики становятся достаточно
жесткими, а двигатель управляемым.
Частотное управление.
Система
частотного управления АД показана на рис. 1-26=
.
Она применяется для управления двигателями с "жесткой"
характеристикой. Здесь меняется частота питания f, с помощью автономного инвертора АИ,=
и
амплитуда напряжения U, с помощью управляемого выпрямителя УВ =
под
управлением управляющего устройства УУ в
зависимости от задаваемой частоты вращения wз.
Вид механических характеристик двигателя при частотном управл=
ении
показан на рис.
1-27. Аналитическое выражение для близкого к линейному рабочего участка
характеристики можно приближенно представить в виде формулы (1-21), из
которой видно, что частота вращения ротора двигателя w
пропорциональна частоте вращения поля статора w1,
которая, в свою очередь, пропорциональна частоте питания f. Амплитуда напряжения питания меняется так, что=
бы
отношение амплитуды и частоты оставалось постоянным k
2.3.
Управление асинхронным двухфазным двигателем (АДД). 2.3.1. Импульсное
управление АДД.
Основным
элементом импульсного управления АДД является двухфазный инвертор, показанн=
ый
на рис.=
2-3.1,а Этот инвертор, состоящий из двух инверторов, формирую=
щих
напряжения переменного тока основной частоты для питания обмотки управления=
(Uоу) и возбуждения (Uов).=
Эти
инверторы должны формировать напряжения, сдвинутые друг относительно друга =
на
90 электрических градусов, причем инвертор, формирующий напряжения Uоу, должен быть управляем=
ым, т.е.
иметь возможность изменять это напряжение по амплитуде (действующему значен=
ию).
Эту функцию можно выполнить с помощью ШИМ на основной или несущей частоте. =
На рис. 2-3.1=
, б показана
временная диаграмма работы инвертора с управлением величиной напряжения Uоу
с помощью ШИМ на основ=
ной
частоте. Здесь для управления АДД изменяется скважность восьми импульсов кл=
ючей
СКЗ, что приводит к сдвигу и изменению по длительности импульсов напряжения=
Uоу, как показано на
рис. 2-3.1=
, б Так как изменение длит=
ельности
импульса
Uоу приводит к изменению действующего
значения основной гармоники, такое управление эквивалентно амплитудно-фазов=
ому
управлению на основной частоте.
2.3.2. Тиристорное
управление АДД.
Аналогичное
амплитудно-фазовое управление АДД при питании его от синусоидального напряж=
ения
можно осуществить с помощью тиристорного
преобразователя, функциональная схема которого показана на рис. 2-3.2=
, а.
Система содержит двухполупериодный преобразоват=
ель Т
мостового типа и схему импульсно-фазового управления этим преобразователем
СИФУ. СИФУ содержит генератор пилообразного напряжения ГПН, компаратор К и формирователь управляющего тиристором импульса Ф.
Временная диаграмма работы преобраователя совме=
стно с
СИФУ показана на рис. 2-3.2, б. СИФУ сравнивает пилообразное напряжение Uп с разностью опорного и =
входного
напряжений Uоп-Uвх, и при равенстве этих напряж=
ений
формирует импульс управления тиристором Uу. Сдв=
иг
импульса Uу относите=
льно
начала периода зависит от Uвх. При Uвх=3D0 сдвиг нулевой, а при Uвх=
=3Dmax
он равен 0,25 Т. Таким образом напряжение управл=
ения Uоу изменяется от 0 до Uс=
.
2.4. Управление шаговыми двигателями. 2.4.1. Система коммутаторов.
Основным
элементом системы управления шаговым двигателем (ШД) является полупроводник=
овый
коммутатор, который переключает фазные токи Iф в обмотках ШД, как показано на рис. 2-4.1=
. Типичная
схема силового ключа СК показана на рис. 2-4.2=
,а,
где диод VD и резистор Rр=
span>
служат для ускорения спада фазного токо при
отключении обмотки транзистором VT. Скорость нарастания фазного тока при
включении VT зависит от величины напряжения питания E и постоянной времени =
цепи
L/(R+Rдоб). Для увел=
ичения
быстродействия систесмы требуется увеличить ско=
рость
нарастания фазных токов при коммутации обмотки. Для этого используется ключ=
с форсировкой, схема которого приведена на рис. 2-4.2=
,б.
Импульсное форсирование заключается в подключении обмотки фазы ШД к источни=
ку
форсирующего напряжения Е2 на время, необходимое=
для
нарастания тока, а после этого обмотка подключается к источнику пониженного
напряжения Е1, обеспечивающему поддержание заданного тока в обмотке. В этой
схеме сперва включаются оба транзистора, а диод VD3 отделяет источник Е2 от источника Е1, затем транзистор VT1 отключается, и
фазный ток идет от Е1 через диод VD3. Характер протекания переходных процес=
сов
в схеме показан на рис. 2-4.2, в.
Наилучшие энергетические соотношения в
контуре управления ШД обеспечивает коммутатор с
импульсной стабилизацией фазовых токов, схема которого показана на рисунке 2-4.3.а . Часть схемы на транзисторах VT3- VTn=
представляет
собой ?????? коммутатор, который питается от источника повышенного=
напряжения<=
span
style=3D'font-family:"Arial +1";color:black'> через импульсный<=
span
style=3D'font-family:"Arial +1";color:black'> стабилизатор тока состоящий из силового транзистора=
VT2, усилителя VT1, компаратора=
K и измерительного резистора Rш. В =
span>этой=
схеме повышенное
напряжение питания E обеспечивает быстрое нарастание<=
span
style=3D'font-family:"Arial +1";color:black'> фазного тока, а импульсный<=
span
style=3D'font-family:"Arial +1";color:black'> стабилизатор ограничивает среднее значение тока в фазе Iф с =
span>помощью широтно-импульсной
модуляции, как показано на рисунке 2-4.3.б . Действие такого коммутатора=
аналогично<=
span
style=3D'font-family:"Arial +1";color:black'> коммутатору=
с форсированием, однако время <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1";
color:black'>форсировки tф здесь задается автоматически за счет обратной связи через резистор Rш=
.
Параметры шагового
привода зависят от
способа коммутации. Наиболее распространенной является
симметричная коммутация, при которой в каждый
такт активизируется одинаковое число обмоток. На рисунке 2-4.4.а показана временная диаграмма =
одинарной =
симметричной коммутации для четырехфазного двигателя, когда в один
такт активизируется одна
фазная обмотка. Большое распространение имеет парная коммутация, при которой в
каждый такт запитываются две
смежные обмотки, как показано <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>на рисунке 2-4.4.б
. И в том
и в другом
случае количество тактов
в цикле n равно количеству фаз двигателя m (в данном
случае m =3D 4 ) и шаг
двигателя =
одинаков при
обоих способах коммутации.
При несимметричной коммутации возможно
уменьшить =
шаг двигателя и тем самым
увеличить =
точность привода.
На рисунке 2-4.5.а
показана <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>временная диаграмма несимметричной =
span>коммутации с
делением <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>шага попалам - режим полушагов. Цикл содержит восемь
тактов (n =3D 2m), но
при этом в
каждый включена либо
одна либо две обмотки,
что приводит к
колебаниям вращающего момоента ШД.
С целью стабилизации вращающего момента можно
уменьшать =
фазовый ток
когда включены две
фазы в ????2 раз с помощью ШИМ,
как показано на
рисунке 2-4.5.а пунктиром. Применение ШИМ дает
возможность плавно изменять
токи в фазах
и добиться большего
дробления =
шага с
целью увеличения точности
и плавности работы
шагового <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>привода - режим мелких
шагов. Временная =
диаграмма такого
режима для четырехфазного ШД показана на
рисунке 2-4.5.б
. Здесь при каждом
положении =
ротора соответствующем "мелкому"
шагу одна обмотка
постоянно =
включена, другая - постоянно выключена, а две остальные переключаются на несущей
частоте с изменяемой скважностью. Величина
мелкого шага зависит
от количества ??????? изменения скважности. Например, =
если скважность задается <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>двухразрядным счетчиком, то происходит дробление шага на 4 и ?????
цикл будет содержать 4*4=3D16 тактов.
2.5 =
Управление вентильными двигателями (ВД)
2.5.1.Принцип действия ВД.
По принципу
действия <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>ВД похож
на двигатель постоянного тока, в котором
коллекторно-????????? узел заменен бесконтактным полупроводниковым коммутатором. ВД имеют инверсное исполнение,т.е. обмотки якоря
расположены в пазах
статора, <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>а ротор
представляет собой постоянный магнит, который может
иметь от одной
до нескольких пар
полюсов. <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>Функциональная схема
ВД показана на
рисунке 2-5.1 . ВД представляет собой систему с
обратной <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>связью по
положению (ротора), которая состоит
из трех основных
частей:
- синхронного
магнитоэлектрического двигателя 1;
- датчика
положения ротора (ДПР) 2;
- системы
управления 3, основным узлом которой является полупроводниковый
коммутатор.
Электромеханическая схема
трехфазного ВД с
одной парой полюсов
на роторе показана
на рисунке 2-5.2 . Здесь на
статоре расположены три
обмотки А, В, С каждая из
которых имеет начало
и конец, например ан,ак и
т. д. В каждый такт коммутации включены <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>две обмотки
так, что они
создают общий поток
Ф1. Коммутация должна
осуществлятся так,
чтобы при переключении поток статора Ф1
опережал <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>поток возбуждения Ф0, создаваемый постоянными магнитами =
ротора, на угол гамма =3D пи/mp, где m - количество фаз,
а p
- количество пар полюсов
на роторе. При гамма отличном от
нуля возникает синхронизирующий момент,
который поворачивает ротор
так чтобы вектора
потоков Ф1 и Ф0 совместились, но при подходе к
согласованному =
span>положению благодоря наличию
датчика положения ротора
( ДПР ) ???????????=
переключении обмоток,
что вызывает поворот
потока Ф1 на угол гамма, ??????? синхронизирующего момента
и т. д. В данном варианте
ВД применен фотоэлектрический ДПР
содержащий три ?????? k, l, m, которые при
повороте <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>ротора перекрываются по очереди шторкой
ДПР и фиксируют положение =
ротора в
виде трехразрядного двоичного кода, принимающего шесть
различных =
значений от
000 до 111 в следующей последовательности 111( показано
на рисунке 2-5.2 ) 110, 100, 000,
001, 011. Система управления должна
осуществить соответствующий каждому
коду ДПР, такую коммутацию обмоток статора, чтобы при
каждом переключении поток
Ф1, опережал поток
Ф0 на угол
гамма и тем
самым обеспечить непрерывность вращения <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>ротора. Существуют два
основных <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>типа коммутации обмоток - 120-градусная и
180-градусная =
коммутации.
2.5.2 120-<=
/span>градусное управление ВД.
При этом
типе управления в
каждый такт остаются
замкнутыми два ключа
коммутатора - один "верхний" и один "нижний" что приводит <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>к подключению к источнику питания
U последовательно <=
/span>двух отмоток
статора, <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>как показано
на рисунке 2-5.3 . На этом
рисунке показан условно
первый такт коммутации в который включены
силовые ключи К1
и К6 и ток протекает по
обмоткам
А <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>и С
как показано на
рисунке стрелкой и
на рисунке 5-2.2 значками "+" и "-". При
повороте <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>ротора на
угол гамма должны
произойти =
перекоммутации обмоток так,
чтобы поток Ф1
повернулся также на
угол гамма. Для этого( см. рисунок 2-5.2 ) должна отключиться обмотка
А, =
обмотка С
остается <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>включенной, а обмотка В подключается так, чтобы ток
в ней прошел
от начала к
концу. Для этого
управляющее устройство должно
снять сигнал U1 и подать на коммутатор сигнал U3 =
который включит
К3, а К1
при этом отключится. Таким образом =
span>УУ должно
ставить в соответствие кодам ДПР k,l,m. Комбинации управляющих сигналов U1-U6 =
span>для соответствующей коммутации обмоток согласно
таблице 2-5.1 Реализации коммутации по этой таблице
соответствует временная диаграмма работы ВД, показанная на рисунок 2-5.4 . Как видно
из диаграммы, при этом способе управления каждый ключ остается
включенным в течении=
двух
тактов управления, т.е. 120???? градусов. При этом на обмотках
якоря формируется трехфазное напряжение с амплитудой 0,5V, так
как обмотки якоря
включаются к источнику V последовательно. =
2.5.3 180-<=
/span>градусное управление ВД.
При таком
управлении в каждой
паре силовых ключей
всегда замкнут один
ключ в течении=
половины
периода коммутации. Поэтому управление ключами можно реализовать более просто непосредственно от сигналов ДПР
как показано на
рисунке 2-5.5 на примере
трехфазного ВД
с четыремя <=
/span>парами полюсов
на роторе. Здесь оптопары располагаются так, чтобы из
восьми возможных комбинаций кодов klm использовались шесть, исключая комбинации 000 и
111, тогда сигналы с
ДПР имеют только
либо два нуля либо
две единицы и
их можно через
соответсвующие формирователи направить =
непосредственно на
управление ключами, получив их
инверсные =
значения U'abc. Последовательность коммутации в этом случае
имеет вид, показанный в
таблице 2-5.2 . Временная диаграмма управления ВД при
180-градусной =
коммутации показана
на рисунке 2-5.6 . Из нее
видно, что каждый
ключ включен в
течении половины <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>периода коммутации т.е. 180 ??градусов, а на обмотках формируется трехфазное напряжение, причем к
каждой обмотке прикладывается напряжение либо +-U/3 либо +- 2U/3, так
как происходит последовательно- паралельное подключение обмоток к источнику питания U - последовательно одна
обмотка и две
других, включенно =
параллельно. При обоих способах коммутации управление скоростью ВД
может осуществляться либо
изменением величины подводимого напряжения U, либо с
помощью ШИМ при
неизменном U, как показано
на рисунке 2-5.3 и рисунке 2-5.5 .
3. Замкнутые электромеханические<=
span
style=3D'font-size:14.0pt;font-family:"Arial medium";color:red'> системы управления
3.1 Принципы построения систем управления
Основным принципом построения систем автоматического управления является принцип
обратной <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>связи. По сложности =
структуры САУ
можно разделить на
две группы:
<=
span
style=3D'mso-list:Ignore'>·&nb=
sp;
одноконтурные САУ; <=
/span>
<=
span
style=3D'mso-list:Ignore'>·&nb=
sp;
многоконтурные САУ. <=
/span>
Структура одноконтурной САУ показана на
рисунке 3-1 . Основными элементами этой структуры являются
задатчик - З, регулятор - Р и
объект управления - ОУ. Система обеспечивает стабилизацию регулируемой величины У или
обработку =
различных типов
задающих <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>воздействий Х(t). В
функции регулятора входит
преобразование =
span>информации об
ошибке Е =3D Х - У в управляющий сигнал U <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>в соответствии с законом ( алгоритмом ) управления. Более сложными
являются <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>многоконтурные системы,
структура =
которых показана
на рисунке 3-2 . Такие системы
кроме информации об
основной <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>регулируемой переменной используют измерение других
координат =
вектора состояния У
и вектора внешних
воздействий М. В электомеханических САУ
получил распространение определенный класс многоконтурных систем
- системы подчиненного управления, структурная схема которых
показана <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>на рисунке 3-3 . В этих
системах <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>объект и
регулятор =
разбиваются на
ряд последовательных звеньев
и структура содержит
ряд вложенных друг
в друга контуров
управления. =
3.1 =
Типовые регуляторы электромехан=
ических САУ
В электромеханических САУ
применяются три типовых
закона управления и
соответствующие <=
/span>им типовые
регуляторы: =
<=
span
style=3D'mso-list:Ignore'>·&nb=
sp;
пропорциональный ( П-регулятор );
<=
span
style=3D'mso-list:Ignore'>·&nb=
sp;
пропорционально-интегральный ( ПИ-регулятор );
<=
span
style=3D'mso-list:Ignore'>·&nb=
sp;
пропорционально-интегрально-дифференциальный
( ПИД-регулятор =
).
3.3 Одноконтурные системы управления
3.3.1 Одноконтурная статическая система стабилизации частоты вращения
Функциональная схема
САР частоты вращения
двигателя =
постоянного тока
показана <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>на рисунке 3-4 . В этой
схеме реализуется пропорциональный закон
управления с помощью
дифференциального=
услилителя=
, на прямой
вход которого подается
напряжение задания Uз
от задатчика,=
а на
инверсный - напряжение обратной
связи Uос от тахогенератора, измеряющего частоту вращения. Сигнал
управления U=3D(<=
span
class=3DSpellE>Uз-Uос)К=
'п подается на
силовую схему вентильного преобразователя <=
/span>и через
него на якорную
цепь двигателя, осуществляя опорное
управление ДПТ. Тахогенератор подключен к ДПТ через
редуктор <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>с коэффициентом передачи <=
span
class=3DSpellE>Кред. Структурная схема
системы без учета
инерционности якорной цепи
ДПТ и тахогенератора ТГ показана на
рисунке 3-5 . Точность системы
характеризуется <=
/span>величиной ошибки
управления дельта w которую можно
совмещать =
с сигналом
рассоглосования Е
через параметры обратной
связи: дельта w =3D =
Е/Кос.
Общая ошибка состоит
из ошибки по
заданию Е' и ошибки по возмущению Е'', которые можно
вычислить =
через передаточные функции по заданию
и возмущению как
показано <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>в выражении ( =
span>3-4
) . Передаточные функции Wе'(p) и
Wе''(p) можно
вычислить =
по структурной схеме системы и
получить <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>их выражения ( 3-5 ) и ( 3-6=
) .
Для анализа точности
системы рассматривают различные режимы:
· =
режим
стабилизации при =
Vз=3Dconst;
· =
режим
движения <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>с постоянным ускорением Vз=
=3DVt;
· =
переходный режим, когда =
Vз изменяется скачком.
Для
статической системы характерно наличие статической ошибки,
которая может быть
вычислена =
по формулам ( 3-3 ) , (=
3-4 ) ,
( =
3-5 ) при t->бесконечности, т.е. р->0. Так
получим для составляющих статической ошибки выражения по формулам ( 3-6
) и (=
3-7 ) .
На рисунке 3-7 показана механическая характеристика =
span>двигателя с
П-регулятором и
без регулятора. При отсутствии регулятора уменьшение частоты вращения, при нагрузке <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>двигателя, дельта w будет выражаться формулой (
3-8 ) , а
при наличии П-регулятора формулой ( 3-7 ) , из сравнения которых видно, что П-регулятор уменьшает статическую ошибку по
возмущению в ( 1+ Кос Кп/Кэм ) раз, т.е.
чем больше Кп, тем меньше статичекая=
ошибка, но она никогда не
может быть сделана
равной 0, =
поэтому такая
система называется статической.
Динамическая ошибка в
такой системе пропорциональна скорости <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>изменения задающего воздействия V. =
span>Изменение частоты
вращения <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>при разгоне
двигателя =
с выходом
на постоянную установку показано <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>на рисунке 3-7 .
Что касается быстродействия системы, <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>то оно
увеличивается при увеличении Кп, как видно из
формулы, <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>например, ( 3-4 ) в которой
постоянная времени уменьшается в ( 1+К ) раз.
3.3.2 Астатическая одноконтурная система регулирования частоты вращения с ПИД-регулятором
Функциональная схема
такой системы с
ДПТ показана на
рисунке 3-8 . Здесь регулятор выполнен <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>на операционном усилителе, имеющем интегрирующую цепочку в обратной
связи и дифференцирующую на
входе.
Структурная схема этой
системы показана на
рисунке 3-9 , где ДПТ
представлен в
виде динамического звена
2-го порядка, ВП-первого порядка, <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>а инерционностью элементов =
в обратной
связи можно пренебречь.
Параметры =
ПИД-регулятора выбираются так, чтобы скомпенсировать две больших постоянных времени ОУ в
данном случае Тм и
Тя, т.е. должны выполняться условия:
Тм=3DТи Кп; ТиТд=3DТмТя
Тогда
числитель =
передаточной функции
регулятора сократится со
знаменателем передаточной функции
ДПТ, т.е.
инерционности компенсируются.
Структурная схема
системы при реализации такой компенсации показана
на рисунке 3-10 . Из этой
схемы можно получить
передаточную функцию замкнутой системы по ошибке
относительно задания, которая выражается формулой (3-9) .
Для оптимального переходного процесса <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>выбирают параметры регулятора так, чтобы коэффициент затухания выражающийся формулой (3-10) , <=
/span>был равен
1/корень(2). При выполнении этого условия получаем
третье соотношение между
параметрами объекта и
регулятора:
2Твп=3DТи/К
Тогда, пренебрегая второй
степенью <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>в знаменателе, получим приближенное выражение для передаточной функции
системы по ошибке
выражение (3-11) . =
Как
видно из (3-11) передаточная функция
имеет в числителе р из-за наличия
интегратора в регуляторе. Поэтому при постоянстве задания Vз=
=3Dconst
получим нулевую статическую ошибку, как видно
из формулы (3-12) . Отсюда система
называется астатической.
Динамическая ошибка, получающаяся при
разгоне двигателя с
постоянным ускорением зависит
от скорости изменения Vз, как видно
из <=
span
style=3D'font-family:"Arial Unicode MS";mso-ascii-font-family:"Arial +1";
mso-hansi-font-family:"Arial +1"'>выражения (3-13) .
Работа системы при
разгоне двигателя с
дальнейшей стабилизацией частоты
вращения <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>показана на
рисунке (3-11) . =
span>
3.4 Двухконтурная система подчиненного управления частотой вращения ДПТ
Функциональная схема такой системы
показана
на рисунке 3-12 здесь аналоговым способом <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>с помощью
операционных усилителей реализованы два
регулятора: =
· =
регулятор тока - PT - ПИ-регулятор;
· =
регулятор частоты вращения - РЧВ - П-регулятор.=
Каждый
регулятор =
включен в
свой контур управления. Внутрений контур
-контур тока-
является <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>подчиненным по
отношению =
к контуру
частоты вращения. РЧВ получает <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>задание от
задатчика в
виде напряжения Uзw и вырабатывает задание для подчиненного ему регулятора тока
в виде напряжения Uз=
i.
Структурная схема системы
показана <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>на рисунке 3-13 , где =
Wз=3DUз=
w/Кос; Iз=3DUзi/Rос.
При применении ПИ-регулятора в контуре тока
получим передаточную функцию
разомкнутого контура тока
в виде формулы (3-14) .
Так как обычно
Тя>Твп, будем компенсировать большую постоянную времени
выбрав <=
span
style=3D'font-family:"Arial Unicode MS";mso-ascii-font-family:"Arial +1";
mso-hansi-font-family:"Arial +1"'>соотношение (3-15) . Подставив эти
значения <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>в (3-14) получим окончательное выражение =
для передаточной функции разомкнутого контура
тока в виде
формулы (3-16) . Из условия
оптимальности переходного процесса
принимают:=
Тиi=3D2kTвп (кси=3D0,707).
Тогда для замкнутого контура получим передаточную функцию в виде
формулы (3-17) . =
span>
Учитывая формулу
(3-17), получим структуреую схему внешнего
контура - =
контура скорости,
показанную на рисунке 3-14 .
При применении в
контуре скорости П-регулятора, как рекомендуется из теории
систем подчиненного управления, получим передаточную функцию
контура скорости в
виде формулы (3-18) . Кэффициент=
передачи П-регулятора Кпс выбирается так, чтобы обеспечить соотношение вида (3-19)
. Тогда получим для
замкнутого контура передаточную функцию в виде
выражения (3-20) . =
3.5 Трехконтурная следящая система
3.5.1 Система без коррекции
Функциональная схема трехконтурной следящей
системы приведена на
рисунке 3-15 . В отличие
от предыдущей двухконтурной системы эта система
имеет третий контур
слежения <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>по углу
фи, т.е.
по положению. Этот контур включает в
себя датчик положения ДП и регулятор положения =
РП, который вырабатывает задание wз=
для контура скорости.
В качестве регулятора положения =
обычно используется П-регулятор. В этом случае при
оптимальном выборе параметров регуляторов тока и
частоты вращения получаем
структурную схему системы
для контура положения, показанную на рисунке 3-16 .
Из структурной схемы можно получить
передаточную функцию замкнутого контура положения в
виде формулы (3-21) для идеального следящего =
привода - без учета инерционности внутренних контуров <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>с эквивалентной постоянной времени
To=3D4Tвп.
Для идеального привода
вводится <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>понятие добротности по скорости Kw=3DKoKрп. Обычно добротность задается <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>в пределах
10-50 с-1, что соответствует постоянной времени краевого
следящего =
привода Тпр=3D0,02-0,1 с.
Типовым режимом следящей
системы является слежение
с постоянной скоростью, когда заданный угол
меняется <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>с постоянной скоростью =
согласно <=
span
style=3D'font-family:"Arial Unicode MS";mso-ascii-font-family:"Arial +1";
mso-hansi-font-family:"Arial +1"'>формуле (3-22) . Учитывая эту
формулу получим выражение для
изображения выходной величины
фи в виде
<=
span
style=3D'font-family:"Arial Unicode MS";mso-ascii-font-family:"Arial +1";
mso-hansi-font-family:"Arial +1"'>формулы (3-23) для идеального привода.
Перейдя от выражения (3-23) во
временную =
область, получим <=
span
style=3D'font-family:"Arial Unicode MS";mso-ascii-font-family:"Arial +1";
mso-hansi-font-family:"Arial +1"'>выражение (3-24) . Для установившегося режима при t->бесконечности получим
выражение (3-25) . Тогда установившаяся ошибка Eсл.уст,
характеризующая <=
/span>точность системы
в установившемся режиме,
будет определяться выражением (3-26) .
Переходные процессы в
идеальной =
и реальной
системах <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>при ступенчатом задании скорости слежения
Vз показаны на
рисунке 3-17 .
Как видно из
из (3-26) и рисунка 3-17 запаздывание системы
Тпр зависит от добротности Кw, а установившееся =
span>ошибка Еуст.сл также
обратно пропорциональна добротности и зависит от
скорости <=
span
style=3D'mso-ascii-font-family:"Arial +1";mso-hansi-font-family:"Arial +1"'=
>изменения угла
задания Vз. =
span>
3.5.2. Следящая система с коррекцией по скорости=
.
Для уменьшения установившейся ошибки в следящих системах ввод=
ят
коррекцию по скорости, для чего задают не только заданный угол поворота, но=
и
скорость его изменения, как показано на структурной схеме рис. 3-18<=
/a>. В
этой схеме задание регулятору положения Uз зави=
сит не
только от угла, но и от его производной (форсировка
по скорости), и определяется выражением (3-27), где К-коэфффициент коррекции (форсир=
овки)
по скорости. Аналогично (3-23) и (3-24) получим выражение для
управляемой величины - формула (3-28).
Отсюда выражение для установившейся ошибки слежения будет иметь вид,
представленный формулой (3-29). При оптимальном выборе коэффициента коррекции
установившаяся ошибка слежения может быть сведена к нулю.
3.5.3. Реализация следящего привода в системах Ч=
ПУ.
В системах числового программ=
ного
управления обычно используются цифро-аналоговые следящие системы с автономн=
ым
приводом, когда цифровая система ЧПУ включена только во внешний контур обра=
тной
связи по положению, а обратные связи по скорости и ток=
уреализуются
в приводе автономно, как показано на рис. 3-19=
.
Обычно в качестве датчика положения ДП используется инкрементный фотоимпульсный датчик ФИД, который преобразует угол
поворота в количество импульсов, преобразуемых в устройстве сопряжения с
приводом УСП в код. Функция регулятора положения с коррекцией по скорости
реализуется в СЧПУ программным путем согласно функциональной схеме,
представленной на рис. 3-20.. Цифромая система =
ЧПУ
работает в дискретном времени с интервалом квантования Т=3D5 мс, который за=
дается
блоком радиальных прерываний БРП. В очередной квант Т задается приращение у=
гла
и вычисляется приращение фактического угла, который накапливается в регистре
данных РД. При постоянстве Т можно рассматривать заданное приращение угла
эквивалентным скорости изменения угла задания. Для получения ошибки
рассогласования по углу необходимо интегрировать разность приращений по всем
квантам времени. Управляющий сигнал, подаваемый на ЦАП, вычисляется по форм=
уле (3-30).=
a>. При
цифровом интегрировании методом прямоугольников эта формула приобретает вид
выражения (3-31).
Соответствующий алгоритм реализации в СЧПУ приведен на рис. 3-20=
..
3.6.
Микропроцессорная реализация САР частоты вращения. 3.6.1. Организация систе=
мы
управления.
Функциональная схема микропроцессорной системы управл=
ения
АДД на основе одноплатного микроконтроллера МС2702 показана на рис. 3-22=
. В
схеме можно выделить следующие основные функциональные<=
/span>
блоки: 1 - микроконтроллер МК; 2 - устройство сопряжения с объектом УСО; 3 -
вентильный преобразователь ВП; 4 - электромеханический блок АДД, ТГ.
Микроконтроллер, принимая в порт ввода-вывода сингналы=
обратной связи по скорости и току, осуществляет управление АДД через вентил=
ьный
преобразователь с помощью таймера Т0 путем фазов=
ого
управления тиристором Т. Основными блоками УСО являются двухканальный АЦП с
коммутатором и формирователем импульсов F1 и F2 с оптронной развязкой ОР. А=
ЦП
под управлением контроллера преобразует последовательно напряжения,
пропорциональные току и частоте вращения в код для их последующей обработки=
в
МК. Вентильный преобразователь осуществляет
амплитудно-фазовое управление АДД с помощью тиристора Т. Электромеханический
блок содержит объект управления АДД и тахогенератор ТГ для осуществл=
ения
обратной связи по частоте вращения. Алгоритм работы системы показан на рис. 3-23=
.
Алгоритм состоит из программного задатчика част=
оты
вращения, регулятора частоты вращения РЧВ, вычисляющего задание следующему =
за
ним регулятору тока Iз в зависимости от заданно=
го и
фактического значений частоты вращения, регулятора тока, вычисляющего код
задания драйверу Кзд и дра=
йера,
вычисляющего код Т0, записываемый в таймер для
управления тиристором. Рассмотрим более подробно программно-аппаратную
реализацию управления тиристорным преобразовате=
лем с
помощью таймера Т0 и программы "драйвер&quo=
t;.
3.6.2.
Реализация тиристорного управления.<=
/p>
В этой системе реализуетcя
импульсно-фазовое управление тиристором с помощью таймера Т0,
который работает в режиме аппаратно управляемого сброса, т.е. формирует
короткий импульс (строб), время задержки которого от с=
инхроимпулься
СИ, подаваемого на управляющий вход Т0, зависит от кода, записываемого
программно (программой драйвер) в регистр счетчика. Синхроимпульс формирует=
ся
от сети питания в начале каждого полупериода с помощью формирователя F1. Та=
ким
образом, таймер Т0 формирует строб, отстоящий от
начала полупериода на заданное время. Этот строб через формирователь F2
управляет включением тиристора, осуществляя импульсно-фазовое управление, к=
ак
показано на рис.
3-24.
При таком управлении действующее значение напряжения
управления Uоу должно
зависеть от кода задания так, как показано на рис 3-25.<=
/a>
При этом время задержки должно меняться от 5 до 10 мс =
(при
частоте питания 50 Гц). При задержке, равной 10 мс, тиристор вообще не успе=
вает
включиться и Uоу=3D0=
, а при
задержке, равной 5 мс тиристор включается полностью и =
Uоу
максимально. При определенной настройке таймера Т0
времени 10 мс соответствует максимальный код, записываемый в регистр таймер=
а FFh. Тогда значению 5 мс будет соответствовать полови=
нный
код: 80h. Программа "драйвер" должна в зависимости от кода задани=
я Кзд вычислить код То, зано=
симый в
таймер Т) согласно графику, показанному на рис 3-26.<=
/a>
Этот график имеет три участка: 1 - рабочий участок; 2 - отсечка; =
3 -
насыщение. На рабочем участке происходит управление тиристором, на участке
отсечки тиристор выключен, а на участке насыщения - полностью включен. Схема
программы "драйвер" показана на рис 3-27.<=
/a>
3.7.
Нечеткое управление электромеханическими объектами.
Нечеткие (=
Fuzzy) системы управления основаны на реализации нече=
ткого
логического вывода типа "Если А, то В"=
и
имеют базу знаний и зачатки искусственного интеллекта. Рассмотрим реализацию
нечеткого управления на примере управления компенсационной емкостью,
функциональная схема которой показана на рис 3-28.=
Здесь объектом управления является компенсационная емкость, с
регулируемым уровнем жидкости в ней. Управление осуществляется по правилу:
"Если уровень высокий, ТО открыть вентиль". В правиле фигурируют
лингвистические переменные, показанные на рис. 3-29.=
Система, принимая значение Х =
по
обратной связи, ставит этому значению в соответсвие
значение лингвистической переменной. Реализация нечеткого вывода показана н=
а рис. 3-30.=
------=_NextPart_01C3E8ED.FBDD66B0
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